Communication transceiver having a three-line balun with power amplifier bias

ABSTRACT

A balun that includes a first conductor, a second conductor, and a third conductor. The first conductor has a first length. The first conductor also has a first end connected to a first balanced power amplifier output port. The second conductor has substantially the same first length. The second conductor also includes a first end connected to a second balanced power amplifier output port and a second end connected to a second end of the first conductor. The third conductor has substantially the same first length. The third conductor has a first end connected to an antenna port and a second end connected to a ground potential.

CROSS REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No.12/461,424, filed Aug. 11, 2009, now U.S. Pat. No. 7,855,613, which is acontinuation of U.S. patent application Ser. No. 12/076,721, filed Mar.21, 2008, now U.S. Pat. No. 7,595,704, which is a continuation of U.S.patent application Ser. No. 11/119,156, filed Apr. 29, 2005, now U.S.Pat. No. 7,385,458, which is a continuation of U.S. patent applicationSer. No. 10/613,346, filed Jul. 2, 2003, now U.S. Pat. No. 6,982,609,which is a continuation in-part of U.S. patent application Ser. No.10/262,336, filed Sep. 30, 2002, now U.S. Pat. No. 7,283,793, whichclaims benefit of U.S. Provisional Application No. 60/381,387, filed May15, 2002, all of which are incorporated herein by reference in theirentirety.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates generally to antenna tuning circuits, andmore particularly, to methods and systems for converting a balanceddifferential signal to an unbalanced signal and applying bias for activecircuits.

2. Description of the Related Art

Transceiver power efficiency is greatly dependant on the efficiency ofthe transmitter power amplifier (PA). An efficient PA converts as muchof the power supply direct current to RF output as possible. PAefficiency is especially important in portable transceiver systems thatrely on a portable power source (e.g., battery) or other transmittersthat have a limited power supply. Many portable transmitters aremanufactured as highly integrated circuits (i.e., transmitter on a chip)so as to exploit the power efficiencies of integrated circuit design.

Some of the potential transmitter inefficiencies can be eliminated orsignificantly reduced in the design of the integrated power amplifiercomponents. However, an integrated PA must still be connected to anantenna, impedance matching network, balancing circuits and othercomponents that are external to the integrated transmitter on a chip.The parasitic capacitance in the output of the on-chip PA may noteffectively be compensated for on the chip. This can be due to loss insignal power in resistive losses of on-chip passive components andineffective use of silicon area due to large tuning components.

FIG. 1 shows a block diagram of a typical prior art transceiver 100. Thetransceiver 100 includes an integrated transmitter 104 that includes adifferential power amplifier 110. The transceiver 100 also includes afront-end circuit 102. The front-end circuit 102 includes a balun 114.The differential PA 110 has a positive potential output 110 p (positiveport) and negative potential output 110 n (negative port). The outputs110 p 110 n of the PA 110 are coupled to the corresponding inputs 114 p,114 n of the balun 114. The output 114A of the balun 114 is coupled toan antenna port 120.

The balun 114 is a balanced signal to unbalanced signal convertercircuit that converts the balanced input signals 110 n, 110 p to anunbalanced or single pole output signal 114A, such as may be coupled tothe single pole antenna port 120 to output a transmitter output signal.

FIG. 2 is a schematic of a typical three-line coupled balun 114. Thebalun 114 includes three lines 202, 204, 206 that are arranged to coupleRF. Typically, each of the three lines 202, 204, 206 have a length of aquarter wavelength (λ/4). The first line 202 is connected to thepositive port (i.e., positive differential output) 110 p of the PAamplifier 110 at a first end and allowed to float, unconnected at asecond end. The second line 204 is connected to the negative port (i.e.negative differential output) 110 n of the PA amplifier 110 at a firstend. A second end of the second line 204 is connected to a groundpotential. The third line 206 is connected to the antenna port 120 atone end while the second end of the third line 206 is connected to aground potential.

In a typical application such as in a 2.45 GHz transmitter outputcircuit, each of the lines 202, 204, 206 has an electrical length of aλ/4 or about 11 millimeters in a material with an effective dielectricconstant of about 7.8. In a typical strip-line application the lines202, 204, 206 are straight layouts that are arranged side by side in oneconductive layer or are vertically aligned in adjacent metal layers. Astraight line that is 11 mm in length is very large when compared to thephysical size of a typical highly integrated transceiver 100.

DC power for the power amplifier devices 110 is typically supplied tothe balun and to the PA through the output ports 110 p, 110 n. However,because the lines 202, 204 are not actually electrically connected as aDC path, then each of the PA output ports 110 p, 110 n require separateDC bias circuits.

Referring again to FIG. 1 above, each of the components in the front-endcircuit 102 (e.g., the balun 114, the antenna 120 and theinterconnecting conductors) has some level of parasitic capacitance thatcan load or otherwise degrade the efficiency of the PA 110. Similarly,each of the DC bias circuits can introduce imbalances in the PA outputports 110 p, 110 n. Requiring two DC bias circuits doubles thecomplexity of the DC bias circuitry, thereby doubling the resultingparasitic capacitance of the DC bias circuitry. Requiring two DC biascircuits also increases the likelihood of unintentionally introducingcircuit imbalances to the PA output ports 110 p, 110 n that can becaused by even relatively slight differences in the two DC biascircuits.

In view of the foregoing, there is a need for a balun that allows asimplified DC bias path and is physically smaller than the prior artbalun 114 while still maintaining the RF port arrangement described inFIGS. 1 and 2 above.

SUMMARY OF THE INVENTION

Broadly speaking, the present invention fills these needs by providing athree-line coupled balun. It should be appreciated that the presentinvention can be implemented in numerous ways, including as a process,an apparatus, a system, computer readable media, or a device. Severalinventive embodiments of the present invention are described below.

One embodiment includes a balun that includes a first conductor, asecond conductor and a third conductor. The first conductor has a firstlength. The first conductor also has a first end connected to a firstbalanced power amplifier output port. The second conductor hassubstantially the same first length. The second conductor also includesa first end connected to a second balanced power amplifier output portand a second end connected to a second end of the first conductor. Thethird conductor has substantially the same first length. The thirdconductor has a first end connected to an antenna port and a second endconnected to a ground potential.

The first length can be substantially equal to an even multiple of thewavelength of a selected center frequency. The first length can besubstantially equal to one-quarter wavelength of a selected centerfrequency.

In one embodiment the balun can also include a biasing network. Thebiasing network can include a fourth conductor that has a first endconnected to the first balanced power amplifier output port and a secondend connected to a bias supply. The fourth conductor can havesubstantially the same first length. The fourth conductor can have alength that has a reactance that offsets a parasitic capacitance of atleast one of the first conductor, the second conductor, the thirdconductor, the first balanced PA port and the second balance PA port.

The first conductor, the second conductor and the third conductor can beformed in a multi-layer structure that includes multiple metal layersthat are interleaved by multiple insulating via layers. The firstconductor can be formed in a first metal layer. The second conductor canbe formed in a second metal layer. The third conductor can be formed ina third metal layer in the multi-layer structure. The second end of thefirst conductor can be connected to the second end of the secondconductor by a via connection formed in a via layer.

The first conductor, the second conductor, and the third conductor canbe substantially, vertically aligned. The multi-layer structure can bebounded by a first ground plane and a second ground plane. The firstground plane and the second ground plane are separated by a distance Hand the first conductor, the second conductor, and the third conductorare vertically offset less than ten times the distance H. Themulti-layer structure can be formed in a homogenous medium. Themulti-layer structure can be formed in at least one of LTCC, BT resin,Silicon, and FR4.

Another embodiment includes a transceiver front-end circuit. Thetransceiver front end circuit includes a first three coupled line balunand a second three coupled line balun. The first three coupled linebalun can include a first conductor, a second conductor and a thirdconductor. The first conductor has a first length and a first endconnected to a first balanced PA output port. The second conductor hassubstantially the same first length. The second conductor includes afirst end connected to a second balanced PA output port and a second endconnected to a second end of the first conductor. The third conductorhas substantially the same first length. The third conductor has a firstend connected to an antenna port and a second end connected to a groundpotential. The second three coupled line balun includes a fourthconductor, a fifth conductor and a sixth conductor. The fourth conductorhas substantially the same first length and a first end connected to afirst balanced LNA input port. The fifth conductor has substantially thesame first length. The fifth conductor includes a first end connected toa second balanced LNA input port and a second end connected to a secondend of the fourth conductor. The sixth conductor has substantially thesame first length and a first end connected to the antenna port and asecond end connected to the ground potential.

The transceiver front-end circuit can also include a first switch and asecond switch. The first switch is connected between the first balancedPA output port and the second balanced PA output port. The second switchconnected between the first balanced LNA input port and the secondbalanced LNA input port.

The transceiver front-end circuit can also include a PA connected to thefirst balanced PA output port and the second balanced PA output port,and a LNA connected to the first balanced LNA input port and the secondbalanced LNA input port. The first switch can be included in the PA andthe second switch can be included in the LNA.

The transceiver front-end circuit can also include a bias networkconnecting a bias source to the first balanced PA output port. The biasnetwork can include a seventh conductor having a substantially the samefirst length.

One embodiment includes a balun that has an operating frequency RFequivalent circuit that includes a first conductor and a secondconductor. The first conductor has a length of about one half wavelengthof a selected center frequency. The first conductor has a first endcoupled to a first balanced PA output port and a second end coupled to asecond balanced PA output port. The second conductor has a length ofabout one quarter wavelength of the selected center frequency and afirst end coupled to the first balanced PA output port and a second endcoupled to an antenna port. The balun has a physical structure thatincludes a third conductor, a fourth conductor, and a fifth conductor.The third conductor having a length of about one quarter wavelength of aselected center frequency and a first end connected to the firstbalanced PA output port. The fourth conductor has a length of about onequarter wavelength of the selected center frequency. The fourthconductor includes a first end connected to the second balanced PAoutput port and a second end connected to a second end of the thirdconductor. The fifth conductor has a length of about one quarterwavelength of the selected center frequency. The fifth conductor has afirst end connected to an antenna port and a second end connected to aground potential.

The fourth conductor and the fifth conductor can be formed in amulti-layer structure that includes multiple metal layers that areinterleaved by multiple insulating via layers. The third conductor canbe formed in a first metal layer. The fourth conductor can be formed ina second metal layer. The fifth conductor can be formed in a third metallayer in the multi-layer structure.

The present invention provides the advantage of a more physicallycompact balun component that also allows biasing of the PA through thebalun and single point tuning for parasitic reactance.

Other aspects and advantages of the invention will become apparent fromthe following detailed description, taken in conjunction with theaccompanying drawings, illustrating by way of example the principles ofthe invention.

BRIEF DESCRIPTION OF THE DRAWINGS

The present invention will be readily understood by the followingdetailed description in conjunction with the accompanying drawings, andlike reference numerals designate like structural elements.

FIG. 1 shows a block diagram of a typical prior art transceiver.

FIG. 2 is a schematic of a typical three-line coupled balun.

FIG. 3 shows an RF equivalent circuit of a class of coupled-line baluns.

FIG. 4A is a schematic of a three-line balun according to one embodimentof the present invention.

FIGS. 4B through 4E illustrate the relationship of the equivalentcircuit 300 to the three-line balun 400 according to one embodiment ofthe present invention.

FIG. 4F is a capacitance diagram of a three-line balun in accordancewith one embodiment of the present invention.

FIG. 5 is an RF equivalent circuit for the three-line balun at theoperating frequency according to one embodiment of the presentinvention.

FIGS. 6A through 6C show a layout view of each of the conductive linesin accordance with one embodiment of the present invention.

FIG. 7 is a three-dimensional view of the three coupled lines as theyare arranged in a multi-layer structure, in accordance with oneembodiment of the present invention.

FIG. 8 is a sectional view of the three coupled lines in accordance withone embodiment of the present invention.

FIG. 9 shows a transceiver circuit that includes a receiver that has alow noise amplifier that has balanced receiver inputs.

DETAILED DESCRIPTION OF THE EXEMPLARY EMBODIMENTS

Several exemplary embodiments for a three-line coupled balun will now bedescribed. It will be apparent to those skilled in the art that thepresent invention may be practiced without some or all of the specificdetails set forth herein.

A three-line coupled balun as described herein allows the poweramplifier to be biased through a single DC input to the balun withoutsignificant impact to the balun's performance. Biasing the PA throughthe balun allows the balun to be used in an open source PA circuit thatis one of the more commonly used PA circuits.

FIG. 3 shows an RF equivalent circuit 300 of a class of coupled-linebaluns. Element 302 is a half-wavelength (λ/2) in length. Element 302 isconnected to the positive port 110 p and the negative port 110 n.Element 306 provides an impedance transformation and couples thesingle-ended port to the half-wavelength line. Baluns with an equivalentcircuit 300 are advantageous because the half-wavelength line connectingthe positive and negative ports collapses to a simple connection from animpedance point of view. That is, whatever reactance (or impedance) isconnected to the positive port also appears at the negative port. Thisproperty can be exploited when simultaneously tuning and DC biasing thetransmitter PA devices.

FIG. 4A is a schematic of a three-line balun 400 according to oneembodiment of the present invention. The balun 400 includes threecoupled lines 402, 404, 406, each having a length of about λ/4. Thecoupled lines 402, 404 are connected together by conductor 408 so as toproduce a DC electrical path between the positive port 110 p and thenegative port 110 n.

λ is equal to one full wave of a center frequency of an RF signal or 360degrees of the RF signal. λ/2 is equal to 180 degrees of the RF signal.Therefore, an RF signal passing along a conductive line that has alength equal to about λ/2 will have about a 180-degree phase shift fromone end of the conductive line to the other. If the signal is reflectedback down the length of the λ/2 conductive line, then the originallyinput RF signal will be phase shifted 180-degrees in each direction or atotal of 360 degrees so that the reflected RF signal is substantiallythe same phase and magnitude of the originally input RF signal andtherefore will not substantially impact or interfere with the originallyinput RF signal. Therefore, a conductive line with a length of about aλ/2 acts as a short to the RF signal. Therefore, if a conductive linebetween positive port 110 p and negative port 110 n is approximately λ/2in length, then an impedance or a capacitance applied at either of thepositive port 110 p or the negative port 110 n will affect the RF signalsubstantially identically felt at both ports 110 p, 110 n.

Conversely, a conductive line having a length of about λ/4 causes aninput RF signal to phase shift approximately 90-degrees and a reflectedRF signal to be phase shifted approximately 180-degrees. A 180-degreephase shift form an RF short and substantially cancels out or interfereswith the originally input RF current. Therefore, a conductive line witha length of about a λ/4 terminated in an RF short acts as an open to theRF circuit. For this reason, a very low impedance applied λ/4 down aconductive line from a port (e.g., either of the positive port 110 p orthe negative port 110 n) will not affect the RF signal at the port.

FIGS. 4B through 4E illustrate the relationship of the equivalentcircuit 300 to the three-line balun 400 according to one embodiment ofthe present invention. FIG. 4B is a single line equivalent circuit 420of the three-line balun 400 if lines 406 and 402 have an insignificantcoupling as will be described in more detail below. Yij are elements ofthe coupled line characteristic admittance matrix. Elements 402, 404,406, 430, 431, 433, 434 represent the admittance between the respectivenodes 120, 110 p, 110 n and intersections of conductors 421, 424, 425,427.

The equivalent circuit 420 can be reduced to the equivalent circuit 440shown in FIG. 4C. The electrical lengths of conductors 425, 424, 421 arethe same. At a selected center frequency, when the electrical lengths ofconductors 425, 424, 421 are equal to λ/4, the equivalent circuit 440can be reduced to the equivalent circuit 460 shown in FIG. 4D. WhenY33=Y22, then the equivalent circuit 460 can be reduced to theequivalent circuit 480 shown in FIG. 4E.

FIG. 4F is a capacitance diagram of a three-line balun 490 in accordancewith one embodiment of the present invention. The multi-layer three-linebalun 490 includes two ground planes 491A, 491B. The three lines 492,493, 494, form the balun 490. Dielectric layers 495A-D separate thelines 492, 493, 494 from one another and the ground planes 491A, 491B.Line 494 is the unbalanced single line side and lines 492, 493 form thebalanced side of the balun 490. Various capacitances are formed betweenthe various conductive paths 492, 493, 494, 491A, 491B. Each of thelines 492, 493, 494 have a respective “self capacitance” C1, C2, C3. Theself-capacitance of each line is equal to the amount of capacitance thatexists between different portions of the line. The self-capacitance C1and C2 of the balanced lines 492, 493 are substantially equal.

A capacitance between the lines 492, 493, 494 also exists. Capacitancesbetween two adjacent layers of the multi-layer balun 490 aresubstantially equal. However the capacitance between two nonadjacentlayers is substantially less than the capacitance between adjacentlayers. By way of example, a capacitance C4 between line 492 and line493 is substantially equal to a capacitance C5 between lines 493 andlines 494. However, a capacitance C6 between line 492 and line 494 issubstantially less than (i.e., at least about ⅕) either of C4 or C5. Theactual amount of the self-capacitance and the capacitances between eachof the lines 492, 493, 494 is determined by the physical geometry of thebalun 490 and the properties of the dielectric that separates the lines.

A characteristic admittance matrix [Y] is related to the capacitancematrix [C] described above by the following relationship:

$\lbrack Y\rbrack = {\frac{1}{\sqrt{\mu ɛ}}\lbrack C\rbrack}$

-   -   where μ is equal to the permeability of the dielectric medium        and    -   where ∈ is equal to the permittivity of the dielectric medium.

The three line baluns described herein have a relatively low propagationloss (e.g., less than about 0.8 db) as the signal passes through thebalun. This relatively propagation low loss is achieved through acombination of a low resistance conductor and low dielectric losses.

While FIG. 4F shows the three-line balun 490 in a multi-layerarrangement, it should be understood that the three lines 492, 493, 494forming the balun 490 could also be arranged in a single conductivelayer with substantially the same capacitive qualities as describedabove in the multi-layer arrangement. Therefore, the present inventionshould not be limited to a multi-layer arrangement.

FIG. 5 is an RF equivalent circuit 500 for the three-line balun 400 atthe operating frequency according to one embodiment of the presentinvention. The equivalent circuit 500 includes a reactive bias andtuning element 510 and a bypass capacitor 520. The reactive bias element510 and the bypass capacitor 520 provide a bias network to couple thebias current from the VDD source. The length of the reactive biaselement 510 can be adjusted to compensate and tune for parasiticcapacitances in the output circuit. Stub 506 provides impedance matchingtuning such as matching a 50-ohm output to a 300-ohm input.

Conductor 408 provides a DC electrical path between the positive port110 p and the negative port 110 n so that a bias voltage VDD can beapplied to one of the ports 110 p, 110 n and will be conducted to theother port. As shown, the bias voltage VDD is connected to the negativeport 110 n.

A tuning stub 510 is used to connect VDD to the negative port 110 n. Thetuning stub 510 can block the RF from entering the bias voltage supplyVDD if the tuning stub has a length of about λ/4. The length of thetuning stub 510 can also be adjusted to compensate for a parasiticcapacitance that may exist in the PA output circuit 400 such as in theantenna port 120 or in one or more of the conductive lines 402, 404,406. As described above, a single parasitic compensation element (e.g.,tuning stub 510) on only one of the balanced ports 110 p, 110 n willeffect the RF signal equally on both of the ports 110 p, 110 n. Becauseonly a single parasitic compensation element is required there is nolonger a requirement of identical or symmetrical tuning elements, whichsimplifies the overall circuit construction and also allows themanufacturing tolerances to be substantially reduced, which can alsoreduce cost and further simplify construction.

FIGS. 6A through 6C show a layout view of each of the conductive lines402, 404, 406, in accordance with one embodiment of the presentinvention. FIG. 6A shows conductive line 402. A first end of theconductive line 402 is connected to the positive PA port 110 p. A secondend of the conductive line 402 is connected to conductive line 404 bythe conductor 408 as will be described in more detail in FIG. 7 below.

FIG. 6B shows conductive line 404. A first end of the conductive line404 is connected to the negative PA port 110 n. A second end of theconductive line 404 is connected to conductive line 402 by the conductor408 as will be described in more detail in FIG. 7 below.

FIG. 6C shows conductive line 406. A first end of the conductive line406 is connected to a ground potential (e.g., a ground plane) throughconductor 412 as will be described in more detail in FIG. 7 below. Asecond end of the conductive line 406 is connected to the antenna port120.

FIG. 7 is a three-dimensional view 700 of the three coupled lines 402,404, 406 as they are arranged in a multi-layer structure, in accordancewith one embodiment of the present invention. The multi-layer structurecan be any strip-line type homogeneous medium such as low temperatureco-fired ceramic (LTCC), silicon, various resins and composite materialssuch as BT resin and FR4 that are well known in the art. Forming thethree coupled lines 402, 404, 406 in a multi-layer structure allows thephysical size of the balun 400 to be compacted over prior art approachesas each layer only has one coupled line that is about λ/4 in length.Each of the coupled lines 402, 404, 406 can be arranged close to itselfso as to further reduce the physical size.

FIG. 8 is a sectional view 800 of the three coupled lines 402, 404, 406,in accordance with one embodiment of the present invention. Thesectional view 800 is not drawn to scale. Specifically the verticaldimensions of the sectional view 800 are exaggerated so as to moreeasily illustrate features and aspects of the three coupled lines 402,404, 406.

The three coupled lines 402, 404, 406 are formed in several metal layersM1, M2, M3. The metal layers M1, M2, M3 are separated by insulating vialayers VIA0, VIA1, VIA2, VIA3. The metal layers M1, M2, M3 and the vialayers VIA0, VIA1, VIA2, VIA3 are bounded by two ground planes 802, 804.More or fewer metal layers and via layers could also be used inalternative embodiments.

H is the distance between the ground planes 802, 804. The three coupledlines 402, 404, 406 can be substantially vertically aligned, as shown.Alternatively, the three coupled lines 402, 404, 406 can be offsethorizontally by an amount less than about 10 H because the majority ofRF signal will be coupled between the three coupled lines 402, 404, 406if the three coupled lines are closer than about 10 times the distance Hbetween the ground planes 802, 804. As the offset distance between thethree coupled lines 402, 404, 406 increases additional amounts of the RFsignal will be coupled directly to one or more of the ground planes 802,804.

In one embodiment, conductors 408 and 412 are formed as vias in vialayers VIA1 and VIA3, respectively. Conductor 408 is formed in via layerVIA1 to connect conductive lines 402, 404 together. Similarly, conductor412 is formed in via layer VIA3 to connect conductive line 406 to groundplane 804.

Referring again to FIGS. 6A and 6B above, fourth conductor (not shown)can be connected to ports 110 p or 110 n by way of a via or located inthe same metal layer M1, M2 respectively. The fourth conductor can formthe tuning stub 510 described in FIG. 5 above to connect the PA biassource 912 (as shown in FIG. 9 below) to the PA output ports 110 n, 110p.

The tuning stub 510 can be a quarter wavelength (λ/4) RF-shorted stub(e.g., through capacitor 520) as a quarter wavelength stub is an open toRF and therefore will protect the signal path form any significant lossof signal. However, if the PA requires reactive tuning, the PA biasnetwork (i.e., tuning stub 510) is not limited to a precise quarterwavelength RF stub and the PA bias network can therefore be adjusted tovarious lengths to provide the desired reactance.

As described above, a coupled three-line balun 400 can be very useful ina transmit signal path (i.e., as part of a transmitter front end circuit102). However, a coupled three-line balun can provide similar benefitsin a receive signal path. FIG. 9 shows a transceiver circuit 900 thatincludes a receiver 904 that has a low noise amplifier 906 that hasbalanced receiver inputs 906 p, 906 n. A receiver balun 902 is includedin the front-end circuit 910. A conductor 908 connects to the receiverbalun 902 to the antenna port 120.

As described above, because the conductive lines 402, 404, 406 are λ/4in length, then the phase of the RF signal is shifted 90 degrees. The90-degree phase shift is reflected back to the beginning of a λ/4conductive line to create a 180-degree phase shift. The 180-degree phaseshift of the RF signal can also be viewed as a 180-degree shift inimpedance. As a result a small impedance at one end of a λ/4 conductiveline is reflected as a very large impedance at the opposite end of theλ/4 conductive line. Therefore, as shown in FIG. 9, if a switch 920 isplaced across the PA ports 110 p, 110 n, then when the switch 920 isclosed (i.e., a closed switch 920 is a short which is a very smallimpedance) then a very large impedance is reflected to the antenna port120. Conversely, if the switch 920 is open (i.e., an open switch 920 isan open circuit which is a large impedance), then a very small impedanceis reflected to the antenna port 120.

Similarly, if a switch 922 is placed across the LNA ports 906 p, 906 n,then when the switch 922 is closed (i.e., a closed switch 922 is a shortwhich is a very small impedance) then a very large impedance isreflected to the antenna port 120. Conversely, if the switch 922 is open(i.e., an open switch 922 is an open circuit which is a largeimpedance), then a very small impedance is reflected to the antenna port120.

As described above, switches 920, 922 can be used to perform atransmit/receive path switching function so that the transmitter 104 andthe receiver 904 can use the same antenna port. By way of example, intransmit mode, switch 922 is closed which reflects a large impedance tothe antenna port 120 and switch 920 is open. Therefore the transmittedRF proceeds out of the PA 110 through the balun 400 to the antenna port120. At the antenna port 120, the RF can travel toward the antenna ortoward the receiver balun 902, however, because switch 922 is closed,the RF sees a large impedance in the receiver balun 902 as compared torelatively small impedance of the antenna. Therefore the majority of thetransmit RF signal continues out the antenna.

Similarly in receive mode, switch 920 is closed which reflects a highimpedance toward the antenna port 120. Switch 922 is open which reflectsa low impedance to the antenna port 120. A small amplitude RF receivesignal enters the antenna 122 to the antenna port 120. At the antennaport 120, the small receive signal sees the large impedance of thetransmit balun 400 and the relatively small impedance of the receivebalun 902. As a result the majority of the receive RF signal isconducted to the receiver balun 902 and into the LNA 906.

Because switches 920 and 922 do not transfer high power signals, theswitches 920, 922 can be relatively small devices. A smaller switchdevice uses less power that a larger switch device so therefore thesmaller switches 920 and 922 are more efficient than a conventional T/Rswitch that is much larger and more complicated.

Another benefit of the three-line coupled balun 400 is the inherentelectrostatic discharge protection function. Since the antenna port 120is tied to ground potential (i.e., ground plane 804) through conductor412, then a static discharge that is received at the antenna port 120will be conducted to ground rather than transferred through the balun400 and into the transmitter 104 or in the case of a receiver balun 902,into the LNA 904.

As used herein the term “about” means +/−10%. By way of example, thephrase “about 250” indicates a range of between 225 and 275.

Although the foregoing invention has been described in some detail forpurposes of clarity of understanding, it will be apparent that certainchanges and modifications may be practiced within the scope of theappended claims. Accordingly, the present embodiments are to beconsidered as illustrative and not restrictive, and the invention is notto be limited to the details given herein, but may be modified withinthe scope and equivalents of the appended claims.

1. A communications device, comprising: a balun circuit including afirst port and a second port, the balun circuit including: a firstconductor having a first length, formed in a first metal layer of amulti-layer structure, the multi-layer structure including a pluralityof metal layers, the first conductor having a first end connected to thefirst port; a second conductor having a second length substantiallysimilar to the first length, formed in a second metal layer of themulti-layer structure, having a first end connected to the firstconductor and a second end connected to the second port; a thirdconductor having a third length substantially similar to the firstlength, formed in a third metal layer of the multi-layer structure,wherein the second metal layer is disposed between the first metal layerand the third metal layer; and a transmitter coupled to the first andthe second port.
 2. The communications device of claim 1, wherein theplurality of metal layers are interleaved by a plurality of insulatinglayers.
 3. The communications device of claim 2, wherein the pluralityof insulating layers includes: a first insulating layer to separate afirst ground plane and the first metal layer; a second insulating layerto separate the first metal layer and the second metal layer; a thirdinsulating layer to separate the second metal layer and the third metallayer; and a fourth insulating layer to separate the third metal layerand a second ground plane.
 4. The communications device of claim 1,further comprising: a fourth conductor, formed in a first insulatinglayer of the multi-layer structure, to connect the first conductor andthe second conductor.
 5. The communications device of claim 1, furthercomprising: a fifth conductor, formed in a first insulating layer of themulti-layer structure, to connect the third conductor to a first groundplane.
 6. The communications device of claim 1, wherein the first lengthis substantially equal to one-quarter wavelength of a selected centerfrequency.
 7. The communications device of claim 1, wherein the baluncircuit includes a fifth port, the third conductor having a first endconnected to the fifth port.
 8. The communications device of claim 7,further comprising: an antenna coupled to the fifth port.
 9. Thecommunications device of claim 1, wherein the transmitter comprises: ashunt switch coupled across the first port and the second port; and apower amplifier having a positive potential output coupled to the firstport and a negative potential output coupled to the second port, theshunt switch being configured to couple the positive potential output tothe negative potential output when closed.
 10. The communications deviceof claim 9, wherein the shunt switch is configured to reflect a firstphase shift of substantially 90 degrees and a second phase shift ofsubstantially 90 degrees through the balun circuit when closed.
 11. Acommunications device, comprising: a balun circuit including a firstport and a second port, the balun circuit including: a first conductorhaving a first length, formed in a first metal layer of a multi-layerstructure, the multi-layer structure including a plurality of metallayers, the first conductor having a first end connected to the firstport; a second conductor having a second length substantially similar tothe first length, formed in a second metal layer of the multi-layerstructure, having a first end connected to the first conductor and asecond end connected to the second port; a third conductor having athird length substantially similar to the first length, formed in athird metal layer of the multi-layer structure, wherein the second metallayer is disposed between the first metal layer and the third metallayer; and a receiver coupled to the first and the second port.
 12. Thecommunications device of claim 11, wherein the plurality of metal layersare interleaved by a plurality of insulating layers.
 13. Thecommunications device of claim 12, wherein the plurality of insulatinglayers includes: a first insulating layer to separate a first groundplane and the first metal layer; a second insulating layer to separatethe first metal layer and the second metal layer; a third insulatinglayer to separate the second metal layer and the third metal layer; anda fourth insulating layer to separate the third metal layer and a secondground plane.
 14. The communications device of claim 11, furthercomprising: a fourth conductor, formed in a first insulating layer ofthe multi-layer structure, to connect the first conductor and the secondconductor.
 15. The communications device of claim 11, furthercomprising: a fifth conductor, formed in a first insulating layer of themulti-layer structure, to connect the third conductor to a first groundplane.
 16. The communications device of claim 11, wherein the firstlength is substantially equal to one-quarter wavelength of a selectedcenter frequency.
 17. The communications device of claim 11, wherein thebalun circuit includes a fifth port, the third conductor having a firstend connected to the fifth port.
 18. The communications device of claim17, further comprising: an antenna coupled to the fifth port.
 19. Thecommunications device of claim 11, wherein the receiver comprises: ashunt switch coupled across the third port and the fourth port; and alow noise amplifier having a positive potential input coupled to thethird port and a negative potential input coupled to the fourth port,the shunt switch being configured to couple the positive potential inputto the negative potential input when closed.
 20. The communicationsdevice of claim 19, wherein the shunt switch is configured to reflect afirst phase shift of substantially 90 degrees and a second phase shiftof substantially 90 degrees through the balun circuit when closed.